Proposed SIW microstrip patch antenna without liquid crystal

Antenna substrate parameters such as thickness, relative permittivity, and loss tangent are critical to the performance of millimeter-wave antennas. The topology of the new SIW patch antenna, shown in Fig. 2, has been inspired by the reference [Reference Awida and Fathy10, Reference Luo, Wang and Zhang34, Reference Kumar, Saravanakumar and Raghavan35].

Fig. 2. Design of the proposed SIW microstrip patch antenna.

In fact, the primary role of the SIW cavity at the back of the patch antenna is to effectively suppress surface wave spurious signals, thereby confining the energy beneath the patch. In this perspective, it is essential to study the leakage characteristics of SIW cavities as a closed resonant structure before they can be added to antenna topologies with open radiation. Here, we address the design issues for the implementation of SIW cavities, including the effect of the via hole diameter and spacing, by identifying suitable designs. Indeed, in order to design the SIW cavity patch antenna presented in Fig. 2 and to determine its most important design parameters, we used the classical equations (4)–(8) cited in [Reference Balanis1] to determine the length and width of the rectangular radiative patch, the latter is supported by an SIW cavity designed using equations (9)–(11) cited in [Reference Sboui, Machac and Gharsallah18, Reference Pozar36, Reference Entesari, Saghati, Sekar and Armendariz37] in the fundamental electrical transverse mode TE110. Metallized vias of diameter d = 0.4 mm and the distance between two vias s = 0.6 mm, which satisfies the conditions (12)–(14) cited in [Reference Deslandes and Wu38], were used to construct an SIW cavity in the planar substrate to form a shield cavity around the patch element. The patch is placed on one side of the substrate. The SIW cavity is formed using four rows of metallized vias, in order to obtain a behavior similar to a classic metal cavity. The operating frequency selected for the antenna design was 28 GHz, a 0.41 mm-thick substrate of Rogers RT4003C type with permittivity ɛ_r = 3.55 is used. The antenna is connected by a 50 ohm microstrip line. The geometric parameters of the proposed antenna are shown in Fig. 2 and listed in Table 2.

Table 2. Dimensions of the proposed SIW microstrip antenna

The width of the patch w is calculated using the equation given below:

(4)$$W_{{\rm patch}} = \displaystyle{c \over {2f_{c\;}\sqrt {( {{\cal E}_r + 1/2} ) } }}$$

where f _c is the center frequency, c the speed of light, and ɛ_r is the relative permittivity.

ɛ_reff is given by the following equation:

(5)$${\cal E}_{reff} = \displaystyle{{{\cal E}_r + 1} \over 2} + \displaystyle{{{\cal E}_r-1} \over 2}\left[{1 + 12\left({\displaystyle{h \over w}} \right)} \right]^{{-}1/2}$$

where h is the thickness of the dielectric substrate.

ΔL, the extended incremental length of the patch, can be calculated using the equations given below:

(6)$$\displaystyle{{\Delta L} \over h} = 0.412\displaystyle{{( {{\cal E}_{reff} + 0.3} ) ( {( {w/h} ) + 0.264} ) } \over {( {{\cal E}_{reff}-0.258} ) ( {( {w/h} ) + 0.8} ) }}$$

The effective length of the patch can be determined by the following equation:

(7)$$L_{eff} = \displaystyle{c \over {2f_c\sqrt {{\cal E}_{reff}} }}$$

The actual length of patch L_patch can be determined by the following equation:

(8)$$L_{\,patch} = L_{eff}-\Delta L$$

The SIW cavity operates in the fundamental electrical transverse mode TE110. The relation between the operating frequency and the length and width of the cavity is revealed by relations (9)–(11) given in [Reference Sboui, Machac and Gharsallah18, Reference Pozar36, Reference Entesari, Saghati, Sekar and Armendariz37]:

(9)$$f_{mnp} = \displaystyle{1 \over {2\sqrt {\mu _r{\cal E}_r} }}\sqrt {{\left({\displaystyle{m \over {L_{eff}}}} \right)}^2 + {\left({\displaystyle{n \over {W_{eff}}}} \right)}^2 + {\left({\displaystyle{\,p \over h}} \right)}^2} $$

(10)$$L_{eff} = L_c-\displaystyle{{1.08d^2} \over s} + \displaystyle{{0.1d^2} \over {L_c}}$$

(11)$$W_{eff} = W_c-\displaystyle{{1.08d^2} \over s} + \displaystyle{{0.1d^2} \over {W_c}}$$

The diameter of the interconnecting via (d) and the spacing (s) between them must meet the following conditions [Reference Deslandes and Wu38]:

(12)$$d \lt \displaystyle{{\lambda _g} \over 5}$$

(13)$$s \le 2d$$

(14)$$\displaystyle{d \over {\lambda _g}} \lt 0.1$$

At this stage, simulation of the antenna is conducted to determine its performances in terms of reflection coefficient and realized gain before adding the liquid crystal, which is done in the second section with the prototype.

The proposed antenna design without the liquid crystal is shown in Fig. 2. The simulation obtained reflection coefficient plot of the antenna and the gain pattern realized without liquid crystal are presented in Figs 3 and 4, respectively.

Fig. 3. Simulated reflection coefficient of proposed SIW microstrip antenna without liquid crystal.

Fig. 4. The simulated realized gain patterns of the proposed SIW microstrip antenna at 28.14 GHz. (a) E-plane (phi = 0°). (b) H-plane (phi = 90°).

The proposed antenna without liquid crystal provides |S ₁₁|> + 10 dB impedance matching throughout a bandwidth ranging from 27.66 to 28.61 GHz, corresponding to a wide bandwidth of 950 MHz with a center resonant frequency equal to 28.14 GHz. This value is sufficient for 5G operations.

Figure 3 illustrates a good reflection coefficient S ₁₁ equal to −31 dB at the resonance frequency 28.14 GHz, and a wide bandwidth approximately equal to 1 GHz.

Figure 4 shows the realized gain pattern polar plot which is directional in the E-plane (phi = 0°) and also directional in the H-plane (phi = 90°) at the resonant frequency of 28.14 GHz with a maximum value of 6.88 dBi and directivity value of 7.53 dBi. In addition, the proposed antenna exhibits excellent radiation efficiency of nearly 91.40% at the resonant frequency.

The proposed antenna performs well without the liquid crystal. In the next section of this manuscript, a parametric study is performed to determine the best location to inject the nematic liquid crystal between the radiative patch and the ground plane to establish reconfigurability.

Proposed SIW microstrip patch antenna loaded with liquid crystal

As mentioned in the introduction, injecting the liquid crystal into an antenna between the top face and the ground plane is the key to exploiting its advantages by adjusting the resonant frequency [Reference Kouki, Sboui and Latrach28, 29, Reference Yang and Wu31, Reference Yaghmaee, Karabey, Bates, Fumeaux and Jakoby32]. In this context, the position of the first layer of the liquid crystal should be limited only by the via of the SIW cavity. Moreover, a parametric study was carried out to determine the dimension of the optimal position for the injection of the liquid crystal, which allows a good adjustment of the reflection coefficient of the antenna. During the parametric study, it was found that the thickness of the LC layer has a significant effect on the matching level of the antenna, as shown in Fig. 5.

Fig. 5. Reflection coefficient S ₁₁ as a function of the thickness of the liquid crystal layer.

Finally, the liquid crystal layer is placed under the patch to obtain the following dimensions: (LLC = 4 mm, WLC = 4.4 mm, z = 0.3 mm) (Fig. 6).

Fig. 6. Design of SIW microstrip patch antenna loaded with nematic liquid crystal (K15).

Frequency tunability

The fabricated antenna prototype is shown in Fig. 7, a conceptual overview of the SIW antenna is shown in Fig. 8, and the fabricated SIW antenna loaded with nematic liquid crystal K15 is shown in Fig. 9. The reflection coefficient of the fabricated SIW antenna loaded with liquid crystal (K15) is measured in free space.

Fig. 7. Fabricated prototype of the proposed SIW antenna.

Fig. 8. Conceptual overview of SIW antenna loaded with nematic liquid crystal K15 under bias magnetic field created by two magnets.

Fig. 9. Fabricated SIW antenna loaded with nematic liquid crystal K15 under bias magnetic field created by two magnets.

After adding a liquid crystal layer (K15) to the antenna without applying magnetic field (H = 0 Oersted, the perpendicular permittivity of the liquid crystal is therefore ɛ_{r ⊥} = 2.72), the simulation results obtained in Fig. 10 show that the resonant frequency increases from 28.14 to 31.716 GHz with reflection coefficient |S ₁₁| = 20.7 dB while the measured results show that the resonant frequency reaches 32 GHz with |S ₁₁| = 15.86 dB.

Fig. 10. Simulated and measured reflection coefficient for different LC permittivities.

The simulation results show that the fabricated antenna loaded with liquid crystal (K15) provides good impedance matching |S ₁₁| > 10 dB when the magnetic field created by two magnets located at 6 mm from both sides of the antenna (Figs 8 and 9; H = 1188 Oersted, the parallel permittivity of liquid crystal ɛ_{r ‖} = 2.9) with the resonant frequency reaching 29.907 GHz at which the reflection coefficient is |S ₁₁| = 34.72 dB. The measured results show that the resonant frequency is at 30.191 GHz with |S ₁₁| = 28.46 dB.

The simulated tunable frequency varies from 29.907 to 31.716 GHz while the measured tunable frequency varies from 30.191 to 32 GHz. In both cases, the tunable frequency varies in a margin of Δfr = 1.809 GHz. The proposed SIW antenna loaded with LC provides good impedance matching |S ₁₁| > 11 dB throughout the whole tuning range.

The measured results are in good agreement with simulation, with just a shifting of 284 MHz resulting from minor fabrication and dielectric characteristics uncertainties, and port losses which are not considered in the simulation.

Radiation performance

Figure 11 shows the simulated electric and magnetic field distributions for the proposed antenna loaded with liquid crystal at the resonant frequency, in the presence and absence of the applied magnetic field (H = 0 Oe; H = 1188 Oe). The colors representing the field distribution on a logarithmic scale range from dark blue (low density) through green and yellow to red (high density). The variation of the E and H field distribution between Figs 11(a) and 11(b) is related to the variation of the relative permittivity of the liquid crystal. Indeed, the presence of the applied magnetic field H = 1188 Oe is reflected in the change of the relative permittivity of the liquid crystal layer used from 2.72 to 2.9, which is the influencing parameter for varying the resonance frequency.

Fig. 11. Electric and magnetic field distributions at resonant frequency.

Figure 12 illustrates the realized gain pattern of the SIW antenna loaded with liquid crystal (K15) in three different scenarios.

Fig. 12. Simulated realized gain patterns versus frequency at H = 0 Oe and H = 1188 Oe.

The first scenario is when the liquid crystal permittivity is equal to ɛ_{r ⊥} = 2.72 and no field is applied at the resonant frequency f = 31.716 GHz, as shown in Fig. 12(a). In the second scenario, the liquid crystal permittivity reaches ɛ_{r ‖} = 2.9 and the applied magnetic field is H = 1188 Oersted at the resonant frequency f = 30.191 GHz, as shown in Fig. 12(b). It can be concluded that the antenna generates an approximately directional radiation pattern for the two main planes E-plane (φ = 0°) and H-plane (φ = 90°) in simulation. In the third scenario, the same conditions prevail as in the second scenario, but considering that the two magnets are placed at a distance of 6 mm in a field area close to the antenna. It can be seen from Fig. 12(c) that the simulated radiation pattern is approximately the same when the two magnets are not considered (Fig. 12(b)). This can be explained by the role of the rows of metallized vias, which form a shield that limits the generated radiation pattern. It can be also noted that the realized gain patterns are almost identical while the antenna is varied in terms of frequency.

In Fig. 13, the maximum realized gain of the SIW patch antenna at the resonance frequency f = 31.716 GHz (H = 0 Oe; ɛ_{r ⊥} = 2.72) reaches a value of 9.07 dBi and the efficiency reaches 94.4%. Even if H = 1188 Oe is applied, resulting in ɛ_{r ‖} = 2.9 at the resonant frequency f = 30.191 GHz, the realized gain reaches 7.61 dBi and the efficiency 93%, considering the two magnets placed 6 mm apart close to the antenna. This roughly confirms the predicted results without considering the magnets (the realized gain reaches 7.89 dBi and the efficiency 93.15%). It can also be noted that the realized gain decreases from 9.07 dB to 7.61 dBi by applying the magnetic field.

Fig. 13. Realized gain versus frequency at H = 0 Oe and H = 1188 Oe.

Table 3 illustrates the performance of the proposed SIW antenna compared to the performance of [Reference Choi, Park, Youn, Hwang, Seong, Whang and Hong20, Reference Kim and Oh25, Reference Tan, Wu, Wang and Poo26, Reference Tan, Wu and Poo27] that use different tunable techniques presented in literature. The proposed SIW antenna loaded with liquid crystal (K15) has the highest gain value (7.61 dBi, 9.07 dBi) and a height radiation efficiency reaching (93%, 94.4%), in simulation both are better than the mentioned works. The measured reflection coefficient S ₁₁ parameter is peaking at −28 dB, better than those of the previously mentioned works. The simulation and measurement results of the conducted work solidify the use of liquid crystals in millimeter waves dedicated to 5G applications. The proposed antenna is characterized by its simplicity and compactness. It also delivers a good range of tunable frequency and excellent gain and efficiency. The proposed SIW antenna loaded with liquid crystal (K15) is thus suitable for many 5G and satellite communication systems.

Table 3. Comparison of the proposed tunable SIW antenna with works presented in literature